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Fig. 1. Interaction between the residual carrier and the data spectrum. (a) Interaction between the residual carrier and the NRZ data spectrum when Br, < Rs. (b) Interaction between the residual carrier and the bi-phase data spectrum when By < Rg. (c) Power spectrum of the residual carrier with square-wave as its subcarrier.

Figure 1 Interaction between the residual carrier and the data spectrum. (a) Interaction between the residual carrier and the NRZ data spectrum when Br, < Rs. (b) Interaction between the residual carrier and the bi-phase data spectrum when By < Rg. (c) Power spectrum of the residual carrier with square-wave as its subcarrier.

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Fig. 2. Effects of interference due to the NRZ data format. (a) ICR versus + for the PCM/PM/NRZ scheme. (b) 7 versus modulation index m when ICR = —15 dB for the PCM/PM/NRZ case. can be considered as additional additive white noise and (14) can be approximated by
Fig. 2. Effects of interference due to the NRZ data format. (a) ICR versus + for the PCM/PM/NRZ scheme. (b) 7 versus modulation index m when ICR = —15 dB for the PCM/PM/NRZ case. can be considered as additional additive white noise and (14) can be approximated by
Fig. 3. Effects of interference due to bi-phase data format. (a) ICR versus 7 for the PCM/PM/bi-phase scheme. (b) 7 versus modulation index m when ICR = —15 dB for the PCM/PM/bi-phase case. In practice, the above case is possible when a data rate of 32 symbols/s is transmitted and a wide carrier tracking mode at 2B, — 300 Hz is selected by the ground station receiver.
Fig. 3. Effects of interference due to bi-phase data format. (a) ICR versus 7 for the PCM/PM/bi-phase scheme. (b) 7 versus modulation index m when ICR = —15 dB for the PCM/PM/bi-phase case. In practice, the above case is possible when a data rate of 32 symbols/s is transmitted and a wide carrier tracking mode at 2B, — 300 Hz is selected by the ground station receiver.
Fig. 4. ICR versus 7 for the PCM/PSK/PM scheme with square-wave subcarrier. 3) PCM/PSK/PM: This scheme is used to separate the residual carrier and the data components so that the interfer- ence caused by the data to the residual carrier is minimized. The higher the subcarrier-frequency-to-data rate ratio the lower the interference. The ICR will be derived for the case of the square-wave subcarrier, and the results can be extended to the sine-wave case very easily. The data component spectrum can be extracted from the transmitted signal spectrum, as given by (9), and is equal to
Fig. 4. ICR versus 7 for the PCM/PSK/PM scheme with square-wave subcarrier. 3) PCM/PSK/PM: This scheme is used to separate the residual carrier and the data components so that the interfer- ence caused by the data to the residual carrier is minimized. The higher the subcarrier-frequency-to-data rate ratio the lower the interference. The ICR will be derived for the case of the square-wave subcarrier, and the results can be extended to the sine-wave case very easily. The data component spectrum can be extracted from the transmitted signal spectrum, as given by (9), and is equal to
Fig. 6. Effective loop SNR versus SSNR for PCM/PM/NRZ (7 = 10), low-data-rate case.
Fig. 6. Effective loop SNR versus SSNR for PCM/PM/NRZ (7 = 10), low-data-rate case.
Fig. 5. Effective loop SNR as a function of SSNR and m for PCM/PM/NRZ. (a) Effective loop SNR versus SSNR for PCM/PM/NRZ (7 = 0.005). (b) Effective loop SNR versus symbol SNR fir PCM/PM/NRZ (m = 1.3 rad).
Fig. 5. Effective loop SNR as a function of SSNR and m for PCM/PM/NRZ. (a) Effective loop SNR versus SSNR for PCM/PM/NRZ (7 = 0.005). (b) Effective loop SNR versus symbol SNR fir PCM/PM/NRZ (m = 1.3 rad).
Fig. 7. Effective loop SNR as a function of SNR for PCM/PM/bi-phase (7 = 0.05). (b) Effective loop SNR versus SSNR for PCM/PM/bi-phase (m = 1.3 rad).
Fig. 7. Effective loop SNR as a function of SNR for PCM/PM/bi-phase (7 = 0.05). (b) Effective loop SNR versus SSNR for PCM/PM/bi-phase (m = 1.3 rad).
Fig. 8. RMS of phase jitter for the PCM/PM/PSK square-wave case. one-sided spectral thermal noise density, No, is given by [1, ch, 5]
Fig. 8. RMS of phase jitter for the PCM/PM/PSK square-wave case. one-sided spectral thermal noise density, No, is given by [1, ch, 5]
Fig. 9. SER for PCM/PM/NRZ. (a) SER versus SSNR for PCM/PM/NRZ + = 0.005). (b) SER versus SSNR for PCM/PM/NRZ (m = 1.3 rad). i.e., by either increasing the data rate or by decreasing the loop noise bandwidth. For Fig. 9(a) and (b) to be useful, they must be used in the operating region of the PLL, as given earlier in Fig. 5(a) and (b). For example, when +y = 0.01 and m = 1.3 rad, Fig. 5(b) indicates that the PLL locks, provided that the SSNR is at least 8 dB. Therefore, when using the performance curve corresponding to the above operating conditions, such as Fig. 9(b), only the region where the SSNR > 8 dB is useful.
Fig. 9. SER for PCM/PM/NRZ. (a) SER versus SSNR for PCM/PM/NRZ + = 0.005). (b) SER versus SSNR for PCM/PM/NRZ (m = 1.3 rad). i.e., by either increasing the data rate or by decreasing the loop noise bandwidth. For Fig. 9(a) and (b) to be useful, they must be used in the operating region of the PLL, as given earlier in Fig. 5(a) and (b). For example, when +y = 0.01 and m = 1.3 rad, Fig. 5(b) indicates that the PLL locks, provided that the SSNR is at least 8 dB. Therefore, when using the performance curve corresponding to the above operating conditions, such as Fig. 9(b), only the region where the SSNR > 8 dB is useful.
Fig. 11. SER versus PCM/PM/bi-phase. (a) SER versus SSNR_ for PCM/PM/bi-phase (7 = 0.05). (b) SER versus SSNR for PCM/PM/bi-phase (m = 133 tad). Fig. 10. SER versus SSNR for PCM/PM/NRZ (7 = 10), low-data-rate case.
Fig. 11. SER versus PCM/PM/bi-phase. (a) SER versus SSNR_ for PCM/PM/bi-phase (7 = 0.05). (b) SER versus SSNR for PCM/PM/bi-phase (m = 133 tad). Fig. 10. SER versus SSNR for PCM/PM/NRZ (7 = 10), low-data-rate case.
Fig. 12. Performance composition of PCM/PM/NRZ and PCM/PM/bi-phase. (a) SER versus SSNR for PCM/PM when m = 1.3 rad. (b) Effective toop SNR versus SSNR for PCM/PM when m = 1.3 rad.
Fig. 12. Performance composition of PCM/PM/NRZ and PCM/PM/bi-phase. (a) SER versus SSNR for PCM/PM when m = 1.3 rad. (b) Effective toop SNR versus SSNR for PCM/PM when m = 1.3 rad.
*NRR = not recommended region. SSNR DEGRADATION WHEN y = 0.005 AND m = 1.1 rad TABLE IV
*NRR = not recommended region. SSNR DEGRADATION WHEN y = 0.005 AND m = 1.1 rad TABLE IV
Fig. 13. Bandwidth occupancy of PCM/PSK/PM versus PCM/PM signals.
Fig. 13. Bandwidth occupancy of PCM/PSK/PM versus PCM/PM signals.
SSNR DEGRADATION WHEN 7y = 0.05 AND m = 1.3 rad *NRR = not recommended region. **PLLNOR = PLL nonoperating region (oe < 8 dB).
SSNR DEGRADATION WHEN 7y = 0.05 AND m = 1.3 rad *NRR = not recommended region. **PLLNOR = PLL nonoperating region (oe < 8 dB).
EFFECTIVE Loop SNR WHEN m = 1.3 rad anp SSNR = 7 dB
EFFECTIVE Loop SNR WHEN m = 1.3 rad anp SSNR = 7 dB
Fig. 14. Measured performance for PCM/PM/NRZ. (a) ICR = —24 dB (m = 1.1 rad, y = 0.001). (b) ICR = —18.6 dB (m = 1.3 rad, 7 = 0.001). (c) ICR = —15.8 dB (m = 1.3 rad, y = 0.002).
Fig. 14. Measured performance for PCM/PM/NRZ. (a) ICR = —24 dB (m = 1.1 rad, y = 0.001). (b) ICR = —18.6 dB (m = 1.3 rad, 7 = 0.001). (c) ICR = —15.8 dB (m = 1.3 rad, y = 0.002).
Fig. 15. Measured performance for PCM/PM/bi-phase. (a) ICR = —59.5 dB (m = 1.1 rad, 7 = 0.001). (b) ICR = ~54.2 dB (m = 1.3 rad, 7 = 0.001). (c) ICR = ~40.2dB (m = 1.3 rad, y = 0.005).
Fig. 15. Measured performance for PCM/PM/bi-phase. (a) ICR = —59.5 dB (m = 1.1 rad, 7 = 0.001). (b) ICR = ~54.2 dB (m = 1.3 rad, 7 = 0.001). (c) ICR = ~40.2dB (m = 1.3 rad, y = 0.005).
Fig. 16. Measured SER for PCM/PSK/PM with square-wave subcarrier m = 1.1 rad and y = 0.001. rad. As a compromise, the PCM/PM/bi-phase scheme can be used with twice the bandwidth of the PCM/PM/NRZ scheme but with much less degradation. However, at a very small loop bandwidth-to-data rate ratio, which at present the DSN receivers are capable of supporting, the performance of the PCM/PM schemes coincides with that of the PCM/PSK/PM scheme. In addition, if one takes into account the subcar- tier loss in the receiver when the PCM/PSK/PM scheme is employed, the performance of PCM/PM schemes becomes as good as, if not better than, that of the PCM/PSK/PM scheme. Moreover, under these conditions the PCM/PM/NRZ scheme becomes the most attractive because it requires the least bandwidth occupancy. If PLL-based receiver implementation is not required, then the BPSK scheme without a residual carrier is most attractive.
Fig. 16. Measured SER for PCM/PSK/PM with square-wave subcarrier m = 1.1 rad and y = 0.001. rad. As a compromise, the PCM/PM/bi-phase scheme can be used with twice the bandwidth of the PCM/PM/NRZ scheme but with much less degradation. However, at a very small loop bandwidth-to-data rate ratio, which at present the DSN receivers are capable of supporting, the performance of the PCM/PM schemes coincides with that of the PCM/PSK/PM scheme. In addition, if one takes into account the subcar- tier loss in the receiver when the PCM/PSK/PM scheme is employed, the performance of PCM/PM schemes becomes as good as, if not better than, that of the PCM/PSK/PM scheme. Moreover, under these conditions the PCM/PM/NRZ scheme becomes the most attractive because it requires the least bandwidth occupancy. If PLL-based receiver implementation is not required, then the BPSK scheme without a residual carrier is most attractive.
Related topics:
Electronic EngineeringMathematicsSymbol error ratePhase ModulationPulse Code ModulationElectrical and Electronic EngineeringPhase shift keying
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